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A Simple Low Cost Acoustic Current Meter

N.L. Brown

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OCEANS 92 Proceedings@m_Mastering the Oceans Through Technology
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INTRODUCTION This paper describes an experimental acoustic current meter presently under development. The objective of the program is to develop a current meter that is inherently low cost, low power consumption, small and yet is capable of excellent performance, both static and dynamic. The rationale for this development is as follows. If the science of climatology and oceanography is to advance significantly it is essential that observations at sea be obtained more frequently and at shorter
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... ographic intervals. The high cost of existing current meters, mooring systems and the ships to deploy them is limiting our understanding of oceanography and climatology. Satellite telemetry has facilitated obtaining data from remote sensors. Hence the oceanographic community is considering expendable moorings, air dropped moorings and possibly moorings deployed from "ships of opportunity". Regardless of which method is used, current meters must be much less expensive, consume much less battery power, be much smaller, lighter and reliable than existing instruments. It should be noted that the size and weight of current meters adversely effects the size and cost of the moorings and the cost of deploying the resulting system. Current meters in routine use today have relatively large, expensive electronics and battery packages and have limited operational life. Current meters using mechanical sensors (rotors or impellers) are vulnerable to damage and are easily stalled by marine fouling or flotsam of various kinds. Existing acoustic current meters using two orthogonal pairs of transducers and an acoustic mirror have poor vertical and horizontal cosine response due to flow interaction with the mirror and the struts used to carry the mooring tension around the pressure housing. These instruments also consume excessive power and hence have limited operational life. All of the above instruments use gimballed compasses (magnetometer or mechanical with optical readout) which tend to be fragile, expensive and of limited accuracy. Existing acoustic instruments transmit pulses [l],[2),[31 or continuous wave bursts [41,[53 simultaneously in opposite directions and then compare the difference in arrival time or phase difference of the received signals to determine the current velocity. They require two receivers, and tend to have errors due to changes in phase shift or time delay differences of the two receivers. Consequently these receivers must be very carefully designed and adjusted to avoid these errors. Typical acoustic path lengths are 10 cm, where an uncertainty of 1 nanosecond in the measurement of time results in an uncertainty of approximately 1.1 cm/sec in velocity. Hence the pulse type sensor requires two wideband receivers and very fast circuitry to measure extremely small time differences. Williams [3] in his BASS design eliminated this particular problem by reversing the receivers and transducers to determine any differences in time delays. The continuous wave type sensor described by the author [43 eliminated the need for very high speed circuits by heterodyning the two received 1.6 mhz carrier frequency signals to obtain a beat frequency of 34 hz and by measuring the phase difference at 34 hz with low power CMOS logic circuits. However this required a second oscillator phase locked to the first at a frequency difference of 34 hz. The requirement of two receivers, the 2nd oscillator and the phase locked loop required a substantial amount of circuits, with a corresponding contribution to overall size, cost and power consumption. The direction sensors in previous designs used either gimballed compass cards with optical readout or gimballed 2 axis fluxgate magnetometers. The compass card design was fragile, expensive and did not have good dynamic response due to inertia of the card and the low magnetic torque inherent in compass cards. Similarly, the gimballed fluxgate designs required jewel bearings to minimize errors due imperfect levelling caused by bearing stickiness, and this in turn required enclosure in an oil filled chamber to provide damping. Figure 1 illustrates external appearance of the proposed final design. At the time of this writing the system was in essentially breadboard form. The existing prototype has a total of 4 axes (see fig. 1 ). Each axis is 15 cm in length and has a vertical separation of 10.5 cm. It can be shown that only one of the four paths will be significantly contaminated by the wake from the center support strut. The microprocessor is used to determine which axis is contaminated by wake from the center support strut, and to reject the data from this axis. This is done by simply determining from which quadrant, in the XY plane, the current is flowing. Only three axes are required for a complete solution of the X, Y and Z components of velocity, thus permitting the accurate determination of current flow essentially uncontaminated by flow interaction with the center strut. THE NEW DESIGN The photographs shown in figures 2 and 3 show the details of the breadboard electronics. These electronics use conventional components on a "through hole" printed circuit board. The small circuit board in figure 2 has the same circuits as the experimental assembly except that it uses surface mount components and packaging with a substantial reduction in size for the same function and will be used in the final design. The design includes a "no moving parts" direction sensor described below. It avoids the need for expensive and fragile gimbals and oil filled damping chambers used in the earlier instruments. It uses a combination of a very low power 3 axis magnetometer and 2 axis accelerometer. The data from these sensors are processed in the microprocessor to determine tilt and magnetic direction, and are combined with velocity sensor outputs to determine the N/S and E/W components for vector averaging. Figure 3 shows the experimental version of the 3 axis magnetometer, which is described in detail below. VELOCITY MEASUREMENT The new design transmits a 1 mhz continuous wave signal for a period of 1 ms, first in one direction where the total phase shift including the receiver phase shift is measured, and then in the opposite direction where the total phase shift is measured again, using the same receiver. The current velocity is proportional to the difference in phase for the two directions. A simple but accurate very low power circuit for measuring phase shift at the carrier frequency has been developed. Since the same receiver is used for both directions the errors due to the different phase shift of two receivers or offset errors in the phase sensitive detector are eliminated when the difference is taken. The theory of operation is as follows. If we consider an acoustic path with two transducers at points A and B where each transducer is alternately transmitting and receiving, we can say that total phase shift between the received and transmitted signals is as follows. Where Θ ta and Θ tb are the phase angles between the applied voltage and the resulting acoustic pressure wave for transducers A and B acting as transmitters. Similarly Θ ra and Θ rb are the phase angles between the output voltage and the arriving acoustic pressure wave for transducers A and B acting as receivers. Θ ttba and Θ ttab are the phase shifts due to the acoustic travel times from A→B and from B→A respectively. Θ rec is the phase shift through the receiver. It can be shown that for any piezo-electric transducer driven by an essentially zero impedance generator or loaded by an essentially zero impedance receiver, the transmitting and receiving phase angles between the electrical current and the acoustic pressure wave are identical. Angular frequency (rads per Sec) d = Distance between transducers A and B (cm) c = Velocity of sound (cm per sec) v = Component of velocity along path A→B ∴ Θ ab -Θ ba = -2ωvd c 2 +v 2 (c>>>v) 2ωd Figure 4 shows a block diagram of the current meter circuit showing just one of the four pairs of transducers and the one set of the switches. The phase shifting circuit output is either 0, 90, 180 or 270 degrees, depending on the command from the microprocessor. The circuit operation is as follows. First the switches Swi and 5w2 are set by the processor to connect transducer A to the transmit circuit and transducer B to the receiver thus transmitting from A to B. Initially the phase shifting network is set to 0 degrees and the output of the phase sensitive detector is digitized by the AID converter and the result is stored. This is repeated for settings of 90, 180 and 270 degrees. The 0 and 180 degree readings are used to determine the "in-phase component" which is directly proportional to the difference between the 0 and 180 degree readings regardless of any DC offset in the phase detector. Similarly the 90 and 270 degree readings are used to obtain the "quadrature" component of the received signal. These two signal components are then used to calculate the phase angle between the received signal and the transmitted signal. The T/R switches Swi and 5w2 are then reversed and the above process repeated to calculate the phase shift for a signal going from B to A. As shown above difference in phase shift for signals going from B to A compared to A to B is then directly proportional to the component of current velocity parallel to the acoustic path between A and B. The above process is then repeated for the remaining 3 acoustic paths and the results are temporarily stored in the micro-processor memory. CURRENT METER CIRCUIT OPERATION For this scheme to work accurately it is necessary that the impedance of both the transmit and the receive circuit be very small compared with impedance of the transducer. When these conditions are met, the phase angle between the acoustic and electrical signals are the same for each transducer whether it is transmitting or receiving thus ensuring the integrity of the phase shift information. As mentioned earlier, this scheme has been breadboarded and tested in the lab at zero velocity, and in the small tow tank at WHOI at speeds to 52 cm/sec. Figures 6a through 6d show that the zero error is less than 0.3 cm/sec and that the phase measuring circuit works well and gives stable and predictable results. It is suspected that the residual errors are due to the "lumpiness" of the soldered connection at the front of the piezo-electric transducers. Lack of a planar surface would result in a distortion of the wave front radiated from the transducer which in turn would result in a different mechanical impedance in the transmission mode compared with the receiving mode where the received wave front is essentially planar. This in turn would tend to disturb the exact reciprocity of the two modes and could result in a non-zero value for O~ -Oba when the velocity (V) was zero. The "noise" of the data when the carriage was at speed was due to the speed fluctuation of the output shaft of the ball and disc variable speed drive of the tow carriage. PHASE MEASURING CIRCUIT The phase sensitive detector shown in figures 4 and 7 ideally can be treated as an analog multiplier whose instantaneous output is the instantaneous product of the two inputs. E s = K s SIN(ωt + Θ s ) E r = K r SIN(ωt + Θ r ) WHERE K 5 , K r are constants ∴ E out = E s x E r = K s K

doi:10.1109/oceans.1992.607655
fatcat:46xx63l4mnbxhju3qvstfso53y