12.1 3D ultrasonic gesture recognition

Richard J. Przybyla, Hao-Yen Tang, Stefon E. Shelton, David A. Horsley, Bernhard E. Boser
2014 2014 IEEE International Solid-State Circuits Conference Digest of Technical Papers (ISSCC)  
Optical 3D imagers for gesture recognition suffer from large size and high power consumption. Their performance depends on ambient illumination and they generally cannot operate in sunlight. These factors have prevented widespread adoption of gesture interfaces in energy-and volume-limited environments such as tablets and smartphones. Wearable mobile devices, too small to incorporate a touchscreen more than a few fingers wide, would benefit from a small, low-power gestural interface. Gesture
more » ... ognition using sound is an attractive alternative to overcome these difficulties due to the potential for chip-scale size, low power consumption, and ambient light insensitivity. Using pulse-echo time-of-flight, MEMS ultrasonic rangers work over distances of up to a meter and achieve sub-mm ranging accuracy [1, 2] . Using a 2-dimensional array of transducers, objects can be localized in 3 dimensions. This paper presents an ultrasonic 3D gesture-recognition system that uses a custom transducer chip and an ASIC to sense the location of targets such as hands. The system block diagram is shown in Fig. 12 .1.1. Targets are localized using pulse-echo time-of-flight methods. Each of the 10 transceiver channels interfaces with a MEMS transducer, and each includes a transmitter and a readout circuit. Echoes from off-axis targets arrive with different phase shifts for each element in the array. The off-chip digital beamformer realigns the signal phase to maximize the SNR and determine target location. The 450μm diameter piezoelectric micromachined ultrasound transducers (pMUTs) used in this work are made up of a 2.2μm thick AlN/Mo/AlN/Al stack deposited on a Si wafer and released with a back-side through-wafer etch. The bottom electrode is continuous, while each pMUT has a top electrode lithographically defined to actuate the trampoline mode. Each pMUT can transmit and receive sound waves, and is operated at its resonance of 217kHz ± 2kHz with a bandwidth of 12kHz. The impedance of the transducers is dominated by the 10pF transducer capacitance, and the motional resistance at resonance is ~2.4MΩ. The resonant frequencies of the pMUTs vary due to fabrication, temperature, and packaging stress, so online frequency tracking is used to maintain maximum SNR during operation. Two pMUTs are used for transmission and seven for reception as illustrated in Fig. 12 .1.1. The receive array is 3.5 wavelengths wide in the x-angle axis, allowing targets separated by more than 15° to be distinguished. In the y-angle axis the array is only 0.16 wavelengths wide, sufficient to determine the y-angle to the target by measuring the average phase difference along the y axis of the array. The center element of the receive array and the element 900μm above it are used to launch a 138μs ≈ 24mm long pulse of sound into the environment. The transmit configuration illuminates a wide field of view, permitting the capture of an entire scene in a single measurement. Applications requiring better target resolution or greater maximum range can also use transmit beamforming at the expense of reduced measurement rate. Each cycle begins with the launch of an acoustic pulse. Figure 12. 1.2 shows the schematic of a single channel. High-voltage level shifters actuate the S TX transmit switches, setting the transducer's bottom electrode to 16V to permit bi-polar actuation of the transducer. The transmitter then excites the transducer with a 32V pp square wave for 30 cycles at the transmit frequency f TX which is locked to 1/16 th of the sampling frequency f s . At the end of the transmit phase, the mechanical energy stored in the inertia of the pMUT dissipates and the pMUT rings down at its natural frequency. The S RX receiver isolation switches are turned on, and a resistor converts the ringdown current to a voltage that is subsequently amplified and digitized by the receiver normally. The ringdown signal is then I/Q demodulated with f TX . The slope of the phase signal during the ringdown indicates the frequency offset and is used to update the f s and f TX used in the next measurement. Figure 12.1.3 shows the offset measured by the frequency autotuning loop as it is enabled. An initial 57kHz offset frequency is nulled to 1kHz within 30 measurement cycles. After 86μs, the ringdown signal has decayed sufficiently for the S ring switch to be opened, beginning the processing of received echoes. At this point, the signal from the transducer is integrated on the transducer's capacitance, and the front-end measures a voltage that is proportional to the displacement of the transducer's membrane. The front-end amplifier consists of an open-loop current-reuse OTA with both NMOS and PMOS differential pairs biased near subthreshold for current efficiency. The front-end current is integrated onto the integrating capacitor of the second stage, which also makes up an integrator in the first of two switched capacitor resonators. Although the second stage is a switched capacitor integrator, the front-end current is processed in a continuous-time fashion before it is sampled at the output of the second integrator. As a result, the second integrator acts as an anti-aliasing filter for the wideband noise generated by the front-end and prevents this noise, the dominant noise source in the receiver architecture, from being aliased into the band of interest. The signal then passes through a second switched-capacitor resonator and is quantized by a comparator. The high in-band gain provided by the 4 th -order bandpass filter shapes the wideband quantization noise to be away from the signal at f TX . The SC resonators are designed to resonate at 1/16 of the sampling frequency f s , which is locked to the transducer's resonance by the ringdown autotuning circuit. This centers the bandpass ΔΣ's noise notch on the signal at f TX . The output of each ΔΣ ADC is I/Q demodulated, filtered, and downsampled offchip. A digital beamformer [3] processes the received signals to maximize the receive SNR and determine the x-angle location of the target. This process can be repeated in the orthogonal angle axis to implement 3D beamforming; in this work we forgo 3D beamforming since the tiny y-axis aperture does not provide any y-axis resolution. Thermal noise in the front-end amplifier and the thermal motion of air limit the minimum detectable echo. The input-referred noise of the amplifier is 11nV/√Hz, and the noise voltage of the transducer is 6nV/√Hz at resonance. Figure 12 .1.4 shows the measured signal-to-noise ratio vs. range for a 127mm×181mm flat rectangular target. Figure 12 .1.4 also shows the rms error in the range and direction measurement. Amplitude noise in the received signal limits the accuracy of the time-of-flight estimate. Figure 12. 1.5 shows the output of the digital beamformer from a single measurement, which captures the echoes from a user's hands and head as he poses as shown. The system tracks objects between 45mm to 1m away and over an angular range of ±45°. Echoes from targets at a range of 1m return after 5.8ms, and this sets the maximum measurement rate of the system at 172 frames per second (fps). Figure 12.1.7 shows a micrograph of the readout IC, which is fabricated in a 0.18μm CMOS process with 32V transistors. For a 1m maximum range, the system presented here uses 13.6μJ per measurement. At 30fps, the receive power consumption is 335μW and the transmit power consumption is 66μW. The energy consumption scales roughly linearly with maximum range. For a maximum range of 0.3m, the energy per frame is reduced to <0.5μJ per channel per frame. Single-element range measurements can be conducted at 10fps using only 5μW. Figure 12.1.6 compares the performance of this system to an earlier MEMS ultrasonic 1D rangefinder [4] and two recent optical 3D rangers [5, 6] . This ultrasonic 3D rangefinder offers dramatically reduced energy consumption compared to optical methods while permitting 3D target tracking. The energy consumption trades off with performance, permitting continuous operation in even tiny mobile devices. These characteristics enable energy-efficient gestural interfaces in applications such as smartphones and tablets, and permit gestural user interfaces in tiny mobile devices too small to accommodate a conventional touchscreen.
doi:10.1109/isscc.2014.6757403 dblp:conf/isscc/PrzybylaTSHB14 fatcat:lc7te32wvvbyzgfx3qcvdbvmri